www.docs.chipfind.ru
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
a
AD8014
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
World Wide Web Site: http://www.analog.com
Fax: 781/326-8703
Analog Devices, Inc., 1999
400 MHz Low Power
High Performance Amplifier
FUNCTIONAL BLOCK DIAGRAMS
FEATURES
Low Cost
Low Power: 1.15 mA Max for 5 V Supply
High Speed
400 MHz, 3 dB Bandwidth (G = +1)
4000 V/ s Slew Rate
60 ns Overload Recovery
Fast Settling Time of 24 ns
Drive Video Signals on 50 Lines
Very Low Noise
3.5 nV/
Hz and 5 pA/
Hz
5 nV/
Hz Total Input Referred Noise @ G = +3 w/500
Feedback Resistor
Operates on +4.5 V to +12 V Supplies
Low Distortion 70 dB THD @ 5 MHz
Low, Temperature-Stable DC Offset
Available in SOIC-8 and SOT-23-5
APPLICATIONS
Photo-Diode Preamp
Professional and Portable Cameras
Hand Sets
DVD/CD
Handheld Instruments
A-to-D Driver
Any Power-Sensitive High Speed System
PRODUCT DESCRIPTION
The AD8014 is a revolutionary current feedback operational
amplifier that attains new levels of combined bandwidth, power,
output drive and distortion. Analog Devices, Inc. uses a propri-
etary circuit architecture to enable the highest performance
amplifier at the lowest power. Not only is it technically superior,
but is low priced, for use in consumer electronics. This general
purpose amplifier is ideal for a wide variety of applications
including battery operated equipment.
The AD8014 is a very high speed amplifier with 400 MHz,
3 dB bandwidth, 4000 V/
s slew rate, and 24 ns settling time.
The AD8014 is a very stable and easy to use amplifier with fast
overload recovery. The AD8014 has extremely low voltage and
current noise, as well as low distortion, making it ideal for use
in wide-band signal processing applications.
For a current feedback amplifier, the AD8014 has extremely
low offset voltage and input bias specifications as well as low
drift. The input bias current into either input is less than 15
A
at +25
C with a typical drift of less than 50 nA/
C over the
industrial temperature range. The offset voltage is 5 mV max
with a typical drift less than 10
V/
C.
For a low power amplifier, the AD8014 has very good drive
capability with the ability to drive 2 V p-p video signals on
75
or 50
series terminated lines and still maintain more
than 135 MHz, 3 dB bandwidth.
SOIC-8 (R)
1
2
3
4
8
7
6
5
AD8014
NC
NC
IN
V
S
NC
+IN
NC = NO CONNECT
V
OUT
+V
S
SOT-23-5 (RT)
1
V
OUT
AD8014
V
S
+IN
2
3
4
5
+V
S
IN
2
REV. B
AD8014SPECIFICATIONS
AD8014AR/RT
Parameter
Conditions
Min
Typ
Max
Units
DYNAMIC PERFORMANCE
3 dB Bandwidth Small Signal
G = +1, V
O
= 0.2 V p-p, R
L
= 1 k
400
480
MHz
G = 1, V
O
= 0.2 V p-p, R
L
= 1 k
120
160
MHz
3 dB Bandwidth Large Signal
V
O
= 2 V p-p
140
180
MHz
V
O
= 2 V p-p, R
F
= 500
170
210
MHz
V
O
= 2 V p-p, R
F
= 500
, R
L
= 50
130
MHz
0.1 dB Small Signal Bandwidth
V
O
= 0.2 V p-p, R
L
= 1 k
12
MHz
0.1 dB Large Signal Bandwidth
V
O
= 2 V p-p, R
L
= 1 k
20
MHz
Slew Rate, 25% to 75%, V
O
= 4 V Step
R
L
= 1 k
, R
F
= 500
4600
V/
s
R
L
= 1 k
2800
V/
s
G = 1, R
L
= 1 k
, R
F
= 500
4000
V/
s
G = 1, R
L
= 1 k
2500
V/
s
Settling Time to 0.1%
G = +1, V
O
= 2 V Step, R
L
= 1 k
24
ns
Rise and Fall Time 10% to 90%
2 V Step
1.6
ns
G = 1, 2 V Step
2.8
ns
Overload Recovery to Within 100 mV
0 V to
4 V Step at Input
60
ns
NOISE/HARMONIC PERFORMANCE
Total Harmonic Distortion
f
C
= 5 MHz, V
O
= 2 V p-p, R
L
= 1 k
68
dB
f
C
= 5 MHz, V
O
= 2 V p-p
51
dB
f
C
= 20 MHz, V
O
= 2 V p-p
45
dB
SFDR
f
C
= 20 MHz, V
O
= 2 V p-p
48
dB
Input Voltage Noise
f = 10 kHz
3.5
nV/
Hz
Input Current Noise
f = 10 kHz
5
pA/
Hz
Differential Gain Error
NTSC, G = +2, R
F
= 500
0.05
%
NTSC, G = +2, R
F
= 500
, R
L
= 50
0.46
%
Differential Phase Error
NTSC, G = +2, R
F
= 500
0.30
Degree
NTSC, G = +2, R
F
= 500
, R
L
= 50
0.60
Degree
Third Order Intercept
f = 10 MHz
22
dBm
DC PERFORMANCE
Input Offset Voltage
2
5
mV
T
MIN
T
MAX
2
6
mV
Input Offset Voltage Drift
10
V/
C
Input Bias Current
+Input or Input
5
15
A
Input Bias Current Drift
50
nA/
C
Input Offset Current
5
A
Open Loop Transresistance
800
1300
k
INPUT CHARACTERISTICS
Input Resistance
+Input
450
k
Input Capacitance
+Input
2.3
pF
Input Common-Mode Voltage Range
3.8
4.1
V
Common-Mode Rejection Ratio
V
CM
=
2.5 V
52
57
dB
OUTPUT CHARACTERISTICS
Output Voltage Swing
R
L
= 150
3.4
3.8
V
R
L
= 1 k
3.6
4.0
V
Output Current
V
O
=
2.0 V
40
50
mA
Short Circuit Current
70
mA
Capacitive Load Drive for 30% Overshoot
2 V p-p, R
L
= 1 k
, R
F
= 500
40
pF
POWER SUPPLY
Operating Range
2.25
5
6.0
V
Quiescent Current
1.15
1.3
mA
Power Supply Rejection Ratio
4 V to
6 V
55
58
dB
Specifications subject to change without notice.
(@ T
A
= +25 C, V
S
= 5 V, R
L
= 150 , R
F
= 1 k , Gain = +2, unless otherwise noted)
3
REV. B
AD8014
AD8014AR/RT
Parameter
Conditions
Min
Typ
Max
Units
DYNAMIC PERFORMANCE
3 dB Bandwidth Small Signal
G = +1, V
O
= 0.2 V p-p, R
L
= 1 k
345
430
MHz
G = 1, V
O
= 0.2 V p-p, R
L
= 1 k
100
135
MHz
3 dB Bandwidth Large Signal
V
O
= 2 V p-p
75
100
MHz
V
O
= 2 V p-p, R
F
= 500
90
115
MHz
V
O
= 2 V p-p, R
F
= 500
, R
L
= 75
100
MHz
0.1 dB Small Signal Bandwidth
V
O
= 0.2 V p-p, R
L
= 1 k
10
MHz
0.1 dB Large Signal Bandwidth
V
O
= 2 V p-p
20
MHz
Slew Rate, 25% to 75%, V
O
= 2 V Step
R
L
= 1 k
, R
F
= 500
3900
V/
s
R
L
= 1 k
1100
V/
s
G = 1, R
L
= 1 k
, R
F
= 500
1800
V/
s
G = 1, R
L
= 1 k
1100
V/
s
Settling Time to 0.1%
G = +1, V
O
= 2 V Step, R
F
= 1 k
24
ns
Rise and Fall Time 10% to 90%
2 V Step
1.9
ns
G = 1, 2 V Step
2.8
ns
Overload Recovery to Within 100 mV
0 V to
2 V Step at Input
60
ns
NOISE/HARMONIC PERFORMANCE
Total Harmonic Distortion
f
C
= 5 MHz, V
O
= 2 V p-p, R
L
= 1 k
70
dB
f
C
= 5 MHz, V
O
= 2 V p-p
51
dB
f
C
= 20 MHz, V
O
= 2 V p-p
45
dB
SFDR
f
C
= 20 MHz, V
O
= 2 V p-p
47
dB
Input Voltage Noise
f = 10 kHz
3.5
nV/
Hz
Input Current Noise
f = 10 kHz
5
pA/
Hz
Differential Gain Error
NTSC, G = +2, R
F
= 500
0.06
%
NTSC, G = +2, R
F
= 500
, R
L
= 50
0.05
%
Differential Phase Error
NTSC, G = +2, R
F
= 500
0.03
Degree
NTSC, G = +2, R
F
= 500
, R
L
= 50
0.30
Degree
Third Order Intercept
f = 10 MHz
22
dBm
DC PERFORMANCE
Input Offset Voltage
2
5
mV
T
MIN
T
MAX
2
6
mV
Input Offset Voltage Drift
10
V/
C
Input Bias Current
+Input or Input
5
15
A
Input Bias Current Drift
50
nA/
C
Input Offset Current
5
A
Open Loop Transresistance
750
1300
k
INPUT CHARACTERISTICS
Input Resistance
+Input
450
k
Input Capacitance
+Input
2.3
pF
Input Common-Mode Voltage Range
1.2
1.1 to 3.9
3.8
V
Common-Mode Rejection Ratio
V
CM
= 1.5 V to 3.5 V
52
57
dB
OUTPUT CHARACTERISTICS
Output Voltage Swing
R
L
= 150
to 2.5 V
1.4
1.1 to 3.9
3.6
V
R
L
= 1 k
to 2.5 V
1.2
0.9 to 4.1
3.8
V
Output Current
V
O
= 1.5 V to 3.5 V
30
50
mA
Short Circuit Current
70
mA
Capacitive Load Drive for 30% Overshoot
2 V p-p, R
L
= 1 k
, R
F
= 500
55
pF
POWER SUPPLY
Operating Range
4.5
5
12
V
Quiescent Current
1.0
1.15
mA
Power Supply Rejection Ratio
4 V to 5.5 V
55
58
dB
Specifications subject to change without notice.
(@ T
A
= +25 C, V
S
= +5 V, R
L
= 150 , R
F
= 1 k , Gain = +2, unless otherwise noted)
SPECIFICATIONS
AD8014
4
REV. B
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD8014 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
ABSOLUTE MAXIMUM RATINGS
1
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12.6 V
Internal Power Dissipation
2
Small Outline Package (R) . . . . . . . . . . . . . . . . . . . . 0.75 W
SOT-23-5 Package (RT) . . . . . . . . . . . . . . . . . . . . . . 0.5 W
Input Voltage Common Mode . . . . . . . . . . . . . . . . . . . . . .
V
S
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . .
2.5 V
Output Short Circuit Duration
. . . . . . . . . . . . . . . . . . . . . . Observe Power Derating Curves
Storage Temperature Range . . . . . . . . . . . . 65
C to +150
C
Operating Temperature Range . . . . . . . . . . . 40
C to +85
C
Lead Temperature (Soldering 10 sec) . . . . . . . . . . . . . +300
C
ESD (Human Body Model) . . . . . . . . . . . . . . . . . . . . +1500 V
NOTES
1
Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only, functional operation of the
device at these or any other conditions above listed in the operational section of this
specification is not implied. Exposure to Absolute Maximum Ratings for any
extended periods may affect device reliability.
2
Specification is for device in free air at 25
C.
8-Lead SOIC Package
JA
= 155
C/W.
5-Lead SOT-23 Package
JA
= 240
C/W.
MAXIMUM POWER DISSIPATION
The maximum power that can be safely dissipated by the AD8014
is limited by the associated rise in junction temperature. The
maximum safe junction temperature for plastic encapsulated
devices is determined by the glass transition temperature of the
plastic. This is approximately +150
C. Even temporarily ex-
ceeding this limit may cause a shift in parametric performance
due to a change in the stresses exerted on the die by the pack-
age. Exceeding a junction temperature of +175
C may result in
device failure.
The output stage of the AD8014 is designed for large load cur-
rent capability. As a result, shorting the output to ground or to
power supply sources may result in a very large power dissipa-
tion. To ensure proper operation it is necessary to observe the
maximum power derating tables.
Table I. Maximum Power Dissipation vs. Temperature
Ambient Temp
Power Watts
Power Watts
C
SOT-23-5
SOIC
40
0.79
1.19
20
0.71
1.06
0
0.63
0.94
+20
0.54
0.81
+40
0.46
0.69
+60
0.38
0.56
+80
0.29
0.44
+100
0.21
0.31
ORDERING GUIDE
Model
Temperature Range
Package Descriptions
Package Options
Brand Code
AD8014AR
1
40
C to +85
C
8-Lead SOIC
SO-8
Standard
AD8014ART
2
40
C to +85
C
5-Lead SOT-23
RT-5
HAA
AD8014AChips
3
40
C to +85
C
Not Applicable
Waffle Pak
Not Applicable
NOTES
1
The AD8014AR is also available in 13" Reels of 2500 each and 7" Reels of 750 each.
2
Except for samples, the AD8014ART is only available in 7" Reels of 3000 each and 13" Reels of 10000 each.
3
The AD8014A Chips are available only in Waffle Pak of 400 each. The thickness of the AD8014A Chip is 12 mils
1 mil. The Substrate should be tied to the +V
S
source.
AD8014
5
REV. B
Typical Performance Characteristics
FREQUENCY MHz
12
15
1
1000
100
10
12
9
6
3
3
6
9
0
G = +1
V
O
= 200mV p-p
R
F
= 1k
R
L
= 1k
V
S
= 5V
V
S
= +5V
15
NORMALIZED GAIN dB
Figure 1. Frequency Response, G = +1, V
S
=
5 V and +5 V
V
S
= 5V
G = +2
R
F
= 500
V
O
= 2V p-p
FREQUENCY MHz
12
15
1
1000
100
10
12
9
6
3
3
6
9
0
R
L
= 50
R
L
= 75
NORMALIZED GAIN dB
Figure 2. Frequency Response, G = +2, V
O
= 2 V p-p
V
S
= 5V
G = +2
R
F
= 1k
R
L
= 1k
FREQUENCY MHz
12
12
10
1000
100
0
9
6
3
3
6
9
V
O
= 0.5V p-p
V
O
= 1V p-p
V
O
= 4V p-p
V
O
= 2V p-p
NORMALIZED GAIN dB
Figure 3. Bandwidth vs. Output Voltage Level--
Dual Supply, G = +2
FREQUENCY MHz
2.0
7.0
1
1000
100
10
6.0
5.0
4.0
3.0
1.0
0
1.0
2.0
NORMALIZED GAIN dB
V
S
= 5V
G = 1
R
F
= 1k
R
L
= 1k
V
O
= 2V
V
O
= 4V
V
O
= 0.2V
V
O
= 0.5V
V
O
= 1V
Figure 4. Bandwidth vs. Output Level--Gain of 1, Dual
Supply
FREQUENCY MHz
12
1
1000
100
10
12
9
6
3
3
6
9
0
NORMALIZED GAIN dB
V
S
= +5V
G = +2
R
F
= 1k
R
L
= 1k
V
O
= 1V p-p
V
O
= 3V p-p
V
O
= 2V p-p
V
O
= 0.5V p-p
Figure 5. Bandwidth vs. Output Level--Single Supply,
G = +2
FREQUENCY MHz
2
1
1000
100
10
8
7
5
4
2
0
1
3
6
1
NORMALIZED GAIN dB
V
S
= +5V
G = 1
R
F
= 1k
R
L
= 1k
V
O
= 2V p-p
V
O
= 0.2V p-p
V
O
= 4V p-p
V
O
= 0.5V p-p
Figure 6. Bandwidth vs. Output Level--Single Supply,
Gain of 1
AD8014
6
REV. B
V
S
= 5V
G = +2
V
O
= 2V p-p
R
L
= 150
FREQUENCY MHz
7.5
1
1000
100
10
6.5
7.0
R
F
= 300
R
F
= 500
R
F
= 600
R
F
= 750
R
F
= 1k
6.0
3.0
3.5
4.5
5.0
5.5
4.0
NORMALIZED GAIN dB
Figure 7. Bandwidth vs. Feedback Resistor--Dual Supply
FREQUENCY MHz
7.5
1
1000
100
10
7.0
6.5
4.0
4.5
5.5
6.0
5.0
NORMALIZED GAIN dB
V
S
= +5V
G = +2
V
O
= 2V p-p
R
L
= 150
R
F
= 300
R
F
= 500
R
F
= 750
R
F
= 1k
Figure 8. Bandwidth vs. Feedback Resistor--Single Supply
G = +2
R
F
= 1k
R
L
= 1k
V
O
= 200mV p-p
1
1000
100
10
6.1
6.5
6.2
6.6
V
S
= 5V
V
S
= +5V
5.6
6.3
6.7
6.8
6.4
FREQUENCY MHz
NORMALIZED GAIN dB
6.0
5.7
5.8
5.9
Figure 9. Gain Flatness--Small Signal
G = +2
V = 2V p-p
R
F
= 500
R
L
= 150
FREQUENCY MHz
1
1000
100
10
5.3
5.8
5.4
5.9
V
S
= 5V
V
S
= +5V
6.2
5.2
5.5
5.6
6.0
6.1
5.7
GAIN FLATNESS dB
Figure 10. Gain Flatness--Large Signal
V
S
= 5V
R
F
= 1k
R
L
= 1k
V
O
= 200mV p-p
1
1000
100
10
15
3
12
0
G = +1
G = +2
9
18
9
3
6
6
G = +10
FREQUENCY MHz
GAIN dB
Figure 11. Bandwidth vs. Gain--Dual Supply, R
F
= 1 k
V
S
= +5V
R
F
= 1k
R
L
= 1k
V
O
= 200mV p-p
1
1000
100
10
15
3
12
0
G = +1
G = +2
9
18
9
3
6
6
G = +10
FREQUENCY MHz
GAIN dB
Figure 12. Bandwidth vs. Gain--Single Supply
AD8014
7
REV. B
V
S
= 5V
G = +2
R
F
= 1k
FREQUENCY MHz
0
100
0.01
1000
50
0.10
1
10
100
40
30
20
10
60
70
80
90
PSRR
+PSRR
PSRR dB
Figure 13. PSRR vs. Frequency
FREQUENCY MHz
20
0.1
1000
50
1
10
100
75
70
65
60
55
45
40
35
30
25
CMRR dB
V
S
= +5V
V
S
= 5V
Figure 14. CMRR vs. Frequency
FREQUENCY MHz
90
1
100
10
DISTORTION dBc 70
50
30
3RD
R
L
= 150
3RD
R
L
= 1k
DISTORTION BELOW
NOISE FLOOR
2ND
R
L
= 1k
2ND
R
L
= 150
Figure 15. Distortion vs. Frequency; V
S
=
5 V, G = +2
140
120
100
80
60
20
0
40
GAIN dB
0
PHASE De
g
rees
40
80
120
160
200
240
280
1k 10k 100k 1M 10M 100M 1G
FREQUENCY Hz
PHASE
GAIN
Figure 16. Transimpedance Gain and Phase vs.
Frequency
FREQUENCY MHz
100
10
1
0.1
0.01
1
1000
10
100
0.1
0.01
OUTPUT RESISTANCE
Figure 17. Output Resistance vs. Frequency, V
S
=
5 V
and +5 V
Figure 18. Settling Time
AD8014
8
REV. B
Note: On Figures 19 and 20 R
F
= 500
, R
S
= 50
and C
L
=
20 pF.
APPLICATIONS
CD ROM and DVD Photodiode Preamp
High speed Multi-X CD ROM and DVD drives require high
frequency photodiode preamps for their read channels. To mini-
mize the effects of the photodiode capacitance, the low imped-
ance of the inverting input of a current feedback amplifier is
advantageous. Good group delay characteristics will preserve the
pulse response of these pulses. The AD8014, having many ad-
vantages, can make an excellent low cost, low noise, low power,
and high bandwidth photodiode preamp for these applications.
Figure 21 shows the circuit that was used to imitate a photo-
diode preamp. A photodiode for this application is basically a
high impedance current source that is shunted by a small ca-
pacitance. In this case, a high voltage pulse from a Picosecond
Pulse Labs Generator that is ac-coupled through a 20 k
resis-
tor is used to simulate the high impedance current source of a
photodiode. This circuit will convert the input voltage pulse into
a small charge package that is converted back to a voltage by the
AD8014 and the feedback resistor.
In this case the feedback resistor chosen was 1.74 k
, which is a
compromise between maintaining bandwidth and providing
sufficient gain in the preamp stage. The circuit preserves the
pulse shape very well with very fast rise time and a minimum of
overshoot as shown in Figure 22.
AD8014
1.74k
20k
49.9
49.9
+5V
5V
OUTPUT
(10 PROBE)
(NO LOAD)
0.1 F
INPUT
Figure 21. AD8014 as a Photodiode Preamp
INPUT
20mV/DIV
1
2
OUTPUT
500mV/DIV
CH1 20.0V
CH2 500mV M 25.0ns CH4
380mV
TEK RUN: 2.0GS/s ET AVERAGE
T[ ]
Figure 22. Pulse Response
Figure 19. Large Signal Step Response; V
S
=
5 V,
V
O
= 4 V Step
Figure 20. Large Signal Step Response; V
S
= +5 V,
V
O
= 2 V Step
AD8014
9
REV. B
DRIVING CAPACITIVE LOADS
The AD8014 was designed primarily to drive nonreactive loads.
If driving loads with a capacitive component is desired, best
settling response is obtained by the addition of a small series
resistance as shown in Figure 26. The accompanying graph
shows the optimum value for R
SERIES
vs. Capacitive Load. It is
worth noting that the frequency response of the circuit when
driving large capacitive loads will be dominated by the passive
roll-off of R
SERIES
and C
L
.
40
30
20
0
10
15
20
25
C
L
pF
10
R
SERIES
5
Figure 26. Driving Capacitive Load
Choosing Feedback Resistors
Changing the feedback resistor can change the performance of
the AD8014 like any current feedback op amp. The table below
illustrates common values of the feedback resistor and the per-
formance which results.
Table II.
3 dB BW
3 dB BW
V
O
= 0.2 V
V
O
= 0.2 V
Gain
R
F
R
G
R
L
= 1 k
R
L
= 150
+1
1 k
Open
480
430
+2
1 k
1 k
280
260
+10
1 k
111
50
45
1
1 k
1 k
160
150
2
1 k
499
140
130
10
1 k
100
45
40
+2
2 k
2 k
200*
180*
+2
750
750
260*
210*
+2
499
499
280*
230*
*V
O
=
1 V.
Video Drivers
The AD8014 easily drives series terminated cables with video
signals. Because the AD8014 has such good output drive you
can parallel two or three cables driven from the same AD8014.
Figure 23 shows the differential gain and phase driving one
video cable. Figure 24 shows the differential gain and phase
driving two video cables. Figure 25 shows the differential gain
and phase driving three video cables.
0.10
0.05
0.00
0.05
0.10
0.60
0.40
0.20
0.20
0.40
0.00
0.60
0.00
0.02
0.04
0.05
0.05
0.05
0.04
0.04
0.04
0.04
0.03
0.00
0.01
0.10
0.21
0.26
0.28
0.29
0.30
0.30
0.30
0.30
1ST
2ND
3RD
4TH
5TH
6TH
7TH
8TH
9TH
10TH
11TH
DIFFERENTIAL
PHASE Degrees
DIFFERENTIAL GAIN %
Figure 23. Differential Gain and Phase R
F
= 500,
5 V, R
L
=
150
, Driving One Cable, G = +2
0.30
0.20
0.10
0.10
0.20
0.60
0.40
0.20
0.20
0.40
0.00
0.60
0.00
0.02
0.03
0.05
0.06
0.06
0.05
0.05
0.07
0.10
0.14
0.00
0.07
0.24
0.40
0.43
0.44
0.43
0.40
0.35
0.26
0.16
1ST
2ND
3RD
4TH
5TH
6TH
7TH
8TH
9TH
10TH
11TH
0.00
0.30
DIFFERENTIAL
PHASE Degrees
DIFFERENTIAL GAIN %
Figure 24. Differential Gain and Phase R
F
= 500,
5 V, R
L
=
75
, Driving Two Cables, G = +2
0.60
0.40
0.20
0.40
0.60
0.00
0.80
0.00
0.44
0.52
0.54
0.52
0.52
0.50
0.48
0.47
0.44
0.45
0.00
0.10
0.32
0.53
0.57
0.59
0.58
0.56
0.54
0.51
0.48
1ST
2ND
3RD
4TH
5TH
6TH
7TH
8TH
9TH
10TH
11TH
0.20
0.80
0.60
0.40
0.20
0.40
0.60
0.00
0.80
0.20
0.80
DIFFERENTIAL
PHASE Degrees
DIFFERENTIAL GAIN %
Figure 25. Differential Gain and Phase R
F
= 500,
5 V, R
L
=
50
, Driving Three Cables, G = +2
AD8014
10
REV. B
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Plastic SOIC
(SO-8)
0.1968 (5.00)
0.1890 (4.80)
8
5
4
1
0.2440 (6.20)
0.2284 (5.80)
PIN 1
0.1574 (4.00)
0.1497 (3.80)
0.0688 (1.75)
0.0532 (1.35)
SEATING
PLANE
0.0098 (0.25)
0.0040 (0.10)
0.0192 (0.49)
0.0138 (0.35)
0.0500
(1.27)
BSC
0.0098 (0.25)
0.0075 (0.19)
0.0500 (1.27)
0.0160 (0.41)
8
0
0.0196 (0.50)
0.0099 (0.25)
x 45
5-Lead Plastic Surface Mount (SOT-23)
(RT-5)
0.1181 (3.00)
0.1102 (2.80)
PIN 1
0.0669 (1.70)
0.0590 (1.50)
0.1181 (3.00)
0.1024 (2.60)
1
3
4
5
0.0748 (1.90)
BSC
0.0374 (0.95) BSC
2
0.0079 (0.20)
0.0031 (0.08)
0.0217 (0.55)
0.0138 (0.35)
10
0
0.0197 (0.50)
0.0138 (0.35)
0.0059 (0.15)
0.0019 (0.05)
0.0512 (1.30)
0.0354 (0.90)
SEATING
PLANE
0.0571 (1.45)
0.0374 (0.95)
C3439b012/99
PRINTED IN U.S.A.
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