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www.fairchildsemi.com

Rev.1.0.0

Features

· Internal Avalanche Rugged Sense FET
· Low startup current (max 40uA)
· Low power consumption under 1 W at 240VAC & 0.4W

load

· Precise Fixed Operating Frequency (66kHz)
· Frequency Modulation for low EMI
· Pulse by Pulse Current Limiting (Adjustable)
· Over Voltage Protection (OVP)
· Over Load Protection (OLP)
· Thermal Shutdown Function (TSD)
· Auto-Restart Mode
· Under Voltage Lock Out (UVLO) with hysteresis
· Built-in Soft Start (15ms)

Application

· SMPS for VCR, SVR, STB, DVD & DVCD
· Adaptor
· SMPS for LCD Monitor

Description

The FSCM0565R is an integrated Pulse Width Modulator
(PWM) and Sense FET specifically designed for high
performance offline Switch Mode Power Supplies (SMPS)
with minimal external components. This device is an
integrated high voltage power switching regulator which
combine an avalanche rugged Sense FET with a current
mode PWM control block. The PWM controller includes
integrated fixed frequency oscillator, under voltage lockout,
leading edge blanking (LEB), optimized gate driver, internal
soft start, temperature compensated precise current sources
for a loop compensation and self protection circuitry.
Compared with discrete MOSFET and PWM controller
solution, it can reduce total cost, component count, size and
weight simultaneously increasing efficiency, productivity, and
system reliability. This device is a basic platform well suited
for cost effective designs of flyback converters.

Table 1. Maximum Output Power

Notes:
1. Typical continuous power in a non-ventilated enclosed

adapter measured at 50

C ambient.

2. Maximum practical continuous power in an open frame

design at 50

C ambient.

3. 230 VAC or 100/115 VAC with doubler.

Typical Circuit

Figure 1. Typical Flyback Application

OUTPUT POWER TABLE

PRODUCT

230VAC

15%

(3)

85-265VAC

Adapt-

(1)

Open

Frame

(2)

Adapt-

(1)

Open

Frame

(2)

FSCM0565RD

50W

65W

40W

50W

FSCM0765RD

65W

70W

50W

60W

FSCM0565RC

70W

85W

60W

70W

FSCM0765RC

85W

95W

70W

85W

Drain

GND

Vfb

Vcc

PWM

OUT

limit

FSCM0565R

Green Mode Fairchild Power Switch (FPS

)

FSCM0565R

Pin Definitions

Pin Configuration

Figure 3. Pin Configuration (Top View)

Pin Number

Pin Name

Pin Function Description

Drain

This pin is the high voltage power SenseFET drain. It is designed to drive the
transformer directly.

GND

This pin is the control ground and the SenseFET source.

Vcc

This pin is the positive supply voltage input. Initially, During start up, the power is
supplied through the startup resistor from DC link. When Vcc reaches 12V, the
power is supplied from auxiliary transformer winding.

Feedback (FB)

This pin is internally connected to the inverting input of the PWM comparator.
The collector of an optocoupler is typically tied to this pin. For stable operation, a
capacitor should be placed between this pin and GND. If the voltage of this pin
reaches 6.0V, the over load protection is activated resulting in shutdown of the
FPS.

I_limit

This pin is for the pulse by pulse current limit level programming. By using a
resistor to GND on this pin, the current limit level can be changed. If this pin is
left floating, the typical current limit will be 2.5A.

FSC

056

1 : Drain

2 : GND

5 : I_limit
4 : FB
3 : Vcc

D2-PAK-5L

0565R

1. Drain

2. GND

3. Vcc

4. FB

5. I_limit

TO-220-5L

FSCM0565RD

FSCM0565RC

FSCM0565R

Absolute Maximum Ratings

(Ta=25

C, unless otherwise specified)

Notes:
1. T

= 25

C to 150

2. Repetitive rating: Pulse width limited by maximum junction temperature
3. L = 30mH, V

= 50V, R

= 25

, starting T

= 25

4. L = 13uH, starting T

= 25

Parameter

Symbol

Value

Unit

Drain-Source (GND) Voltage

(1)

DSS

650

Drain-Gate Voltage (R

=1M

)

DGR

650

Gate-Source (GND) Voltage

Drain Current Pulsed

(2)

Continuous Drain Current (TO-220)
@ Tc = 25°C
@ T

=100

3.2

Continuous Drain Current (D2-PAK)
@ Tc = 25°C
@ T

=100

2.9

1.9

Supply Voltage

Analog Input Voltage Range

-0.3 to V

Total Power Dissipation (D2-PAK)

Derating

0.6

Total Power Dissipation (TO-220)

120

Derating

0.96

Operating Junction Temperature

Internally limited

Operating Ambient Temperature

-25 to +85

Storage Temperature Range

STG

-55 to +150

ESD Capability, HBM Model (All pins
excepts for Vstr and Vfb)

2.0

(Vcc-Vfb=1.0kV)

ESD Capability, Machine Model (All pins
excepts for Vstr and Vfb)

300

(Vcc-Vfb=100V)

FSCM0565R

Electrical Characteristics

(Ta = 25

C unless otherwise specified)

Parameter Symbol

Condition

Min.

Typ.

Max.

Unit

Sense FET SECTION

Drain source breakdown voltage

DSS

= 0V, I

= 250

650

Zero gate voltage drain current

DSS

= Max, Rating

= 0V

500

Static drain source on resistance

DS(ON)

= 10V, I

= 2.3A

1.76

2.2

Output capacitance

OSS

= 0V, V

= 25V,

f = 1MHz

Turn on delay time

D(ON)

= 325V, I

= 5A

(MOSFET switching
time is essentially
independent of
operating temperature)

Rise time

Turn off delay time

D(OFF)

Fall time

CONTROL SECTION

Initial frequency

OSC

=14V, V

=5V

kHz

Modulated frequency range

mod

±3

kHz

Frequency modulation cycle

mod

Voltage stability

STABLE

10V

17V

Temperature stability

OSC

+85

±5

±10

Maximum duty cycle

MAX

Minimum duty cycle

MIN

Start threshold voltage

START

=GND

Stop threshold voltage

STOP

=GND

Feedback source current

=GND

0.7

0.9

1.1

Soft-start time

BURST MODE SECTION

Burst Mode Voltages

Vcc=14V

0.4

0.5

0.6

Vcc=14V

0.24

0.3

0.36

FSCM0565R

Typical Performance Characteristics

(These Characteristic Graphs are Normalized at Ta= 25

Startup Current vs. Temp

Start Threshold Voltage vs. Temp

Stop Threshold Voltage vs. Temp

Initial Freqency vs. Temp

Maximum Duty Cycle vs. Temp

Feedback Source Current vs. Temp

0.60

0.80

1.00

1.20

1.40

1.60

-50

-25

100 125

Junction Temperature()

S
t
a
r
t
up C

u
r
r
e
n
t

(
N

o
r
m

a
l
i
zed

t
o

2
5

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100 125

Junction T emperature()

S
t
a
r
t
T

h
r
e
s
hol

d

V

o
l
t
a
ge

(
N

l
i
z
e
d
t
o
25

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100 125

Junction Temperature()

S
t
op T

h
r
e
s
hol

d V

o
l
t
a
g
e

(
N

o
r
m

a
liz

e
d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100 125

Junction Temperature()

I
n
itia

l F

r
e
q
u
e
n
c
y

(
N

o
r
m

a
lize

d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100 125

Junction Temperature()

a
xi

m D

u
t
y
C

y
c
l
e

(
N

o
r
m

a
lize

d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction T emperature()

F
B

o
u
r
ce C

u
r
r
en

(
N

o
r
m

a
liz

e
d
to

)

FSCM0565R

Typical Performance Characteristics

(Continued)

(These Characteristic Graphs are Normalized at Ta= 25

ShutDown Feedback Voltage vs. Temp

ShutDown Delay Current vs. Temp

Bust Mode Enable Volage vs. Temp

Burst Mode Disable Voltage vs. Temp

Mavimum Drain Current vs. Temp

Operating Supply Current vs. Temp

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction Temperature()

S
h
ut

d
o
w

n F

o
l
t
a
g
e

(
N

o
r
m

a
liz

e
d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction T emperature()

h
ut

n
D

e
l
a
y

r
r
e
n

(
N

o
r
m

a
liz

e
d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction T emperature()

u
r
s
t
M

o
d
e
E

n
a
b
le

o
lt
a
g
e

(
N

o
r
m

a
li
zed

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction Temperature()

u
r
s
t
M

ode

i
s
a
bl

e

V

o
l
t
a
g
e

(
N

o
r
m

a
lize

d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100

125

Junction Temperature()

a
xi

mum D

r
a
i
n C

u
r
r
e
n
t

(
N

o
r
m

a
liz

e
d
to

)

0.80

0.88

0.96

1.04

1.12

1.20

-50

-25

100 125

Junction Temperature()

p
e
r
a
t
i
n
g S

upp

l
y
C

u
r
r
e
nt

(
N

a
l
i
z
e
d
t
o
25

)

FSCM0565R

Functional Description

Startup : Figure 4 shows the typical startup circuit and

transformer auxiliary winding for FSCM0565R application.
Before FSCM0565R begins switching, FSCM0565R
consumes only startup current (typically 25uA) and the
current supplied from the DC link supply ccurrent consumed
by FPS (Icc) and charges the external capacitor (C

) that is

connected to the Vcc pin. When Vcc reaches start voltage of
12V (V

START

), FSCM0565R begins switching, and the

current consumed by FSCM0565R increases to 3mA. Then,
FSCM0565R continues its normal switching operation and
the power required for this device is supplied from the
transformer auxiliary winding, unless Vcc drops below the
stop voltage of 8V (V

STOP

). To guarantee the stable operation

of the control IC, Vcc has under voltage lockout (UVLO)
with 4V hysteresis. Figure 5 shows the relation between the
current consumed by FPS (Icc) and the supply voltage (Vcc).

Figure 4. Startup circuit

Figure 5. Relation between operating supply current and

Vcc voltage

The minimum current supplied through the startup resistor is
given by

where V

line

min

is the minimum input voltage, V

start

is the

start voltage (12V) and R

str

is the startup resistor. The startup

resistor should be chosen so that I

sup

min

is larger than the

maximum startup current (40uA). If not, Vcc can not be
charged to the start voltage and FPS will fail to start up.

2. Feedback Control : FSCM0565R employs current mode
control, as shown in Figure 6. An opto-coupler (such as the
H11A817A) and shunt regulator (such as the KA431) are
typically used to implement the feedback network.
Comparing the feedback voltage with the voltage across the
Rsense resistor makes it possible to control the switching
duty cycle. When the reference pin voltage of the KA431
exceeds the internal reference voltage of 2.5V, the
H11A817A LED current increases, thus pulling down the
feedback voltage and reducing the duty cycle. This event
typically happens when the input voltage is increased or the
output load is decreased.

2.1 Pulse-by-pulse current limit: Because current mode
control is employed, the peak current through the Sense FET
is determined by the inverting input of PWM comparator
(Vfb*) as shown in Figure 6. When the current through the
opto transistor is zero and the current limit pin (#5) is left
floating, the feedback current source (I

) of 0.9mA flows

only through the internal resistor (R+2.5R=2.8k). In this
case, the cathode voltage of diode D2 and the peak drain
current have maximum values of 2.5V and 2.5A, respec-
tively. The pulse-by-pulse current limit can be adjusted using
a resistor to GND on current limit pin (#5). The current limit
level using an external resistor (R

LIM

) is given by

Figure 6. Pulse width modulation (PWM) circuit

FSCM0565R

Rstr

Vcc

sup

AC line

line

min

- V

line

max

)

Icc

Vcc

Vstop=8V

25uA

3mA

Vstart=12V

Power Up

Power Down

Isup

min

2 V

line

min

start

(

)

Rstr

------------

LIM

2.5A

2.8k

LIM

------------------------------------

OSC

Vcc

Vref

delay

2.5R

Gate

driver

OLP

Vfb

KA431

H11A817A

sense

SenseFET

LI M

0.9mA

0.3k

FSCM0565R

2.2 Leading edge blanking (LEB) : At the instant the
internal Sense FET is turned on, there usually exists a high
current spike through the Sense FET, caused by primary-side
capacitance and secondary-side rectifier reverse recovery.
Excessive voltage across the Rsense resistor would lead to
incorrect feedback operation in the current mode PWM
control. To counter this effect, the FSCM0565R employs a
leading edge blanking (LEB) circuit. This circuit inhibits the
PWM comparator for a short time (T

LEB

) after the Sense FET

is turned on.

3. Protection Circuit : The FSCM0565R has several self
protective functions such as over load protection (OLP), over
voltage protection (OVP) and thermal shutdown (TSD).
Because these protection circuits are fully integrated into the
IC without external components, the reliability can be
improved without increasing cost. Once the fault condition
occurs, switching is terminated and the Sense FET remains
off. This causes Vcc to fall. When Vcc reaches the UVLO
stop voltage of 8V, the current consumed by FSCM0565R
reduces to the startup current (typically 25uA) and the
current supplied from the DC link charges the external
capacitor (C

) that is connected to the Vcc pin. When Vcc

reaches the start voltage of 12V, FSCM0565R resumes its
normal operation. In this manner, the auto-restart can
alternately enable and disable the switching of the power
Sense FET until the fault condition is eliminated (see Figure
7).

Figure 7. Auto restart operation

3.1 Over Load Protection (OLP) : Overload is defined as
the load current exceeding a pre-set level due to an
unexpected event. In this situation, the protection circuit
should be activated in order to protect the SMPS. However,

even when the SMPS is in the normal operation, the over
load protection circuit can be activated during the load
transition. In order to avoid this undesired operation, the over
load protection circuit is designed to be activated after a
specified time to determine whether it is a transient situation
or an overload situation. Because of the pulse-by-pulse
current limit capability, the maximum peak current through
the Sense FET is limited, and therefore the maximum input
power is restricted with a given input voltage. If the output
consumes beyond this maximum power, the output voltage
(Vo) decreases below the set voltage. This reduces the
current through the opto-coupler LED, which also reduces
the opto-coupler transistor current, thus increasing the
feedback voltage (Vfb). If Vfb exceeds 2.5V, D1 is blocked
and the 5.3uA current source (I

delay

) starts to charge C

slowly up to Vcc. In this condition, Vfb continues increasing
until it reaches 6V, when the switching operation is
terminated as shown in Figure 8. The delay time for
shutdown is the time required to charge C

from 2.5V to

6.0V with 5.3uA (I

delay

). In general, a 10 ~ 50 ms delay time

is typical for most applications.

Figure 8. Over load protection

3.2 Over voltage Protection (OVP) : If the secondary side
feedback circuit were to malfunction or a solder defect
caused an open in the feedback path, the current through the
opto-coupler transistor becomes almost zero. Then, Vfb
climbs up in a similar manner to the over load situation,
forcing the preset maximum current to be supplied to the
SMPS until the over load protection is activated. Because
more energy than required is provided to the output, the
output voltage may exceed the rated voltage before the over
load protection is activated, resulting in the breakdown of the
devices in the secondary side. In order to prevent this
situation, an over voltage protection (OVP) circuit is
employed. In general, Vcc is proportional to the output
voltage and the FSCM0565R uses Vcc instead of directly
monitoring the output voltage. If V

exceeds 19V, an OVP

circuit is activated resulting in the termination of the
switching operation. In order to avoid undesired activation of
OVP during normal operation, Vcc should be designed to be
below 19V.

Fault

situation

12V

Vcc

Vds

Fault

occurs

Fault

removed

Normal

operation

Normal

operation

Power

t
t
t
t

2.5V

6.0V

Over load protection

= Cfb*(6.0-2.5)/I

delay

FSCM0565R

3.3 Thermal Shutdown (TSD) : The Sense FET and the
control IC are built in one package. This makes it easy for
the control IC to detect the heat generation from the Sense
FET. When the temperature exceeds approximately 145

the thermal protection is triggered resulting in shutdown of
FPS.

4. Frequency Modulation : EMI reduction can be
accomplished by modulating the switching frequency of a
switched power supply. Frequency modulation can reduce
EMI by spreading the energy over a wider frequency range
than the band width measured by the EMI test equipment.
The amount of EMI reduction is directly related to the depth
of the reference frequency. As can be seen in Figure 9, the
frequency changes from 63KHz to 69KHz in 4ms.

Figure 9. Frequency Modulation

5. Soft Start : The FSCM0565R has an internal soft start
circuit that increases PWM comparator inverting input
voltage together with the Sense FET current slowly after it
starts up. The typical soft start time is 15msec, The pulse
width to the power switching device is progressively
increased to establish the correct working conditions for
transformers, rectifier diodes and capacitors. The voltage on
the output capacitors is progressively increased with the
intention of smoothly establishing the required output
voltage. It also helps to prevent transformer saturation and
reduce the stress on the secondary diode during startup.

6. Burst operation : In order to minimize power dissipation
in standby mode, the FSCM0565R enters into burst mode
operation at light load condition. As the load decreases, the
feedback voltage decreases. As shown in Figure 10, the

device automatically enters into burst mode when the
feedback voltage drops below V

(300mV). At this point

switching stops and the output voltages start to drop at a rate
dependent on standby current load. This causes the feedback
voltage to rise. Once it passes V

(500mV) switching

resumes. The feedback voltage then falls and the process
repeats. Burst mode operation alternately enables and
disables switching of the power Sense FET thereby reducing
switching loss in standby mode.

Figure 10. Waveforms of burst operation

Drain current

66kHz

69kHz

63kHz

4ms

Vds

0.3V

0.5V

Ids

set

time

Switching

disabled

T2 T3

Switching

disabled

FSCM0565R

Typical application circuit

Features

· High efficiency (>81% at 85Vac input)
· Low standby mode power consumption (<1W at 240Vac input and 0.4W load)
· Low component count
· Enhanced system reliability through various protection functions
· Low EMI through frequency modulation
· Internal soft-start (15ms)

Key Design Notes

· The delay time for over load protection is designed to be about 50ms with C106 of 47nF. If a faster triggering of OLP is

required, C106 can be reduced to 22nF.

· Using a resistor R106 on the current limit pin (#5), the pule-by-pulse current limit level is reduced to about 2A.
· Zener diode ZD102 is used for a safety test such as UL. When the drain pin and feedback pin are shorted, the zener diode

fails and remains short, which causes the fuse (F1) blown and prevents explosion of the opto-coupler (IC301). This zener
diode also increases the immunity against line surge.

1. Schematic

Application

Output power

Input voltage

Output voltage (Max current)

LCD Monitor

40W

Universal input

(85-265Vac)

5V (2.0A)

12V (2.5A)

C102

220nF

275VAC

LF101
23mH

C101

220nF

275VAC

RT1

5D-9

FUSE

250V

C103

100uF

400V

R103

56k

C104

2.2nF

1kV

D101

UF 4007

C106
47nF

50V

C105
22uF

50V

D102

TVR10G

R104

EER3016

BD101

2KBP06M3N257

R101

560k

FSCM0565RC

limit

Vfb

Vcc

Drain

GND

ZD101

22V

D202

MBRF10100

C201

1000uF

25V

C202

1000uF

25V

L201

12V, 2.5A

D201

MBRF1045

C203

1000uF

10V

C204

1000uF

10V

L202

5V, 2A

R201

R202

1.2k

R204

5.6k

R203

10k

C205
47nF

R205

5.6k

C301

4.7nF

IC301

H11A817A

IC201

KA431

R102

500k

R105

500k

R106
10k

1/4W

ZD102

10V

FSCM0565R

2. Transformer Schematic Diagram

3.Winding Specification

4.Electrical Characteristics

5. Core & Bobbin

Core : EER 3016
Bobbin : EER3016
Ae(mm2) : 96

Pin (s

Wire

Turns

Winding Method

0.2

Center Winding

Insulation: Polyester Tape t = 0.050mm, 2Layers

Np/2

0.4

Solenoid Winding

Insulation: Polyester Tape t = 0.050mm, 2Layers

12V

0.3

Center Winding

Insulation: Polyester Tape t = 0.050mm, 2Layers

N5V

0.3

Center Winding

Insulation: Polyester Tape t = 0.050mm, 2Layers

Np/2

0.4

Solenoid Winding

Outer Insulation: Polyester Tape t = 0.050mm, 2Layers

Pin

Specification

Remarks

Inductance

1 - 3

570uH ± 10%

100kHz, 1V

Leakage Inductance

1 - 3

10uH Max

all short

EER3016

12V

FSCM0565R

6.Demo Circuit Part List

Part

Value

Note

Part

Value

Note

Fuse

C301

4.7nF

Polyester Film Cap.

F101

2A/250V

NTC

Inductor

RT101

5D-9

L201

5uH

Wire 1.2mm

Resistor

L202

5uH

Wire 1.2mm

R101

560K

R102

500K

1/4W

R103

56K

R104

1/4W

Diode

R105

500K

1/4W

D101

UF4007

R106

10K

1/4W

D102

TVR10G

R201

1/4W

D201

MBRF1045

R202

10K

1/4W

D202

MBRF10100

R203

1.2K

1/4W

ZD101

22V Zener diode

R204

5.6K

1/4W

ZD102

10V Zener diode

R205

5.6K

1/4W

Bridge Diode

BD101

2KBP06M 3N257

Bridge Diode

Capacitor

C101

220nF/275VAC

Box Capacitor

Line Filter

C102

220nF/275VAC

Box Capacitor

LF101

23mH

Wire 0.4mm

C103

100uF/400V

Electrolytic Capacitor

C104

10nF/1kV Ceramic

Capacitor

IC101

FSCM0565RC

FPS

(7A,650V)

C105

22uF/50V

Electrolytic Capacitor

IC201

KA431(TL431)

Voltage reference

C106

47nF/50V

Ceramic Capacitor

IC301

H11A817A

Opto-coupler

C201

1000uF/25V

Electrolytic Capacitor

C202

1000uF/25V

Electrolytic Capacitor

C203

1000uF/10V

Electrolytic Capacitor

C204

1000uF/10V

Electrolytic Capacitor

C205

47nF/50V

Ceramic Capacitor

FSCM0565R

1/13/05 0.0m 001

2005 Fairchild Semiconductor Corporation

LIFE SUPPORT POLICY
FAIRCHILD'S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES

OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR

CORPORATION. As used herein:

1. Life support devices or systems are devices or systems

which, (a) are intended for surgical implant into the body,

or (b) support or sustain life, and (c) whose failure to

perform when properly used in accordance with

instructions for use provided in the labeling, can be

reasonably expected to result in a significant injury of the

user.

2. A critical component in any component of a life support

device or system whose failure to perform can be

reasonably expected to cause the failure of the life support

device or system, or to affect its safety or effectiveness.

www.fairchildsemi.com

DISCLAIMER
FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO ANY

PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME ANY

LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN; NEITHER

DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS.

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