WIRELESS COMMUNICATIONS DIVISION

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TQ9222

DATA SHEET

Dual-Band TDMA

LNA/Downconverter IC

Features

Pin compatible with TQ5121

Single 3 V operation

Low-current operation

Low-frequency IF capability

Excellent ½ IF rejection

IF output combining

matched inputs (most ports)

QSOP-24 plastic package

Applications

IS-136 dual-band Mobile Phones

Tri-Mode Phones

GSM dual-band Mobile Phones

Wireless local loop

Product Description

The TQ9222 is a 3-V, RF receiver IC designed specifically for dual-band TDMA
applications. Its RF performance meets the requirements of products designed to
the IS-136 and GSM standards. The TQ9222 is pin compatible with TQ5121 (cellular
band LNA/Mixer) which enables handset designers to use strategic board platform
strategy.

The TQ9222 contains two separate LNA+Mixer circuits to handle both the 800 MHz
cellular band and the 1900 MHz PCS band. The mixers use a high-side LO
frequency, with the IF covering a range of 70-140 MHz. IF frequencies below 120
MHz are possible due to the ½-IF spurious signal rejection in the 1900 MHz
LNA+Mixer. The IF outputs are designed for use of a common IF frequency. Most
RF ports are internally matched to 50

, greatly simplifying the design and keeping

the number of external components to a minimum. Separate supply voltage
connections provide the required flexibility for dual-band operation. The TQ9222
achieves good RF performance with low current consumption, supporting long
standby times in portable applications. Coupled with the very small QSOP-24
package, the part is ideally suited for dual-band mobile phones.

Electrical Specifications

Parameter

Typ

Units

Gain

800 band

1900 band

17.5
17.5

MHz
MHz

Noise Figure

800 band

1900 band

2.7
3.0

dB
dB

Input 3

Order Intercept

800 band

1900 band

-9.0
-9.0

dBm
dBm

DC supply Current

800 band

1900 band

10.0
22.0

mA
mA

Note 1: Test Conditions: Vdd=2.8V, Ta=25C, filter IL=2.5dB, RF

=881MHz, RF

=1960MHz,

=991MHz, LO

= 2070MHz, IF=110MHz, LO Input=-7dBm; unless otherwise specified

LNA OUT

1900

Vdd

MXR 1900

MXR LO

1900

Vdd LNA

1900

LNA IN

1900

Vdd LNA

800

LNA IN

800

LNA OUT

800

Vdd

MXR 800

MXR LO

800

MXR RF

800

MXR IF

800

MXR IF

1900

MXR RF

1900

TQ9222

Data Sheet

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Electrical Characteristics

Parameter

Conditions

Min.

Typ/Nom

Max.

Units

RF Frequency

Cellular band
PCS band

869

1930

894

1990

MHz
MHz

LO Frequency

Cellular band
PCS band

950

2010

1040
2140

MHz
MHz

IF Frequency

Cellular band

140

MHz

LO input level

-7

-4

dBm

Supply voltage

2.7

2.8

3.0

Gain

Cellular band
PCS band

16.0
16.0

17.5
17.5

dB
dB

Gain Variation vs. Temp.

-40 to 85C

-2.0

+2.0

Noise Figure

Cellular band
PCS band

2.7
3.0

3.5
3.5

dB
dB

Input 3

Order Intercept

Cellular band
PCS band

-11.0
-11.0

-9.0
-9.0

dBm
dBm

Return Loss
Cellular and PCS band

LNA input external match
LNA output

Mixer RF input
Mixer LO input

10
10

dB
dB

Isolation

Cellular and PCS bands

LO to LNA in

LO to IF; after IF match
RF to IF; after IF match

40
40

dB
dB

IF Output Impedance

Cellular and PCS band

Vdd = 2.8V; "ON"

Vdd = 0V; "OFF"

500

<50

Ohm

Supply Current

Cellular band
PCS band

10
22

mA
mA

Note 1: Test Conditions: Vdd=2.8V, Ta=25C, filter IL=2.5dB, RF

=881MHz, RF

=1960MHz, LO

=991MHz, LO

= 2070MHz, IF=110MHz, LO Input=-7dBm; unless

otherwise specified

Absolute Maximum Ratings

Parameter

Value

Units

DC Power Supply

5.0

Power Dissipation

500

Operating Temperature

-40 to 85

Storage Temperature

-60 to 150

Signal level on inputs/outputs

+20

dBm

Voltage to any non supply pin

-.3 to +.3

TQ9222
Data Sheet

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Typical Performance

Test Conditions: TQ9222 Low Band (Unless Otherwise Specified): Vdd=2.8V, Ta=25C, filter IL=2.5dB, RF=881MHz, LO=991MHz, IF=110MHz, LO input=-7dBm

Conversion Gain vs. Freq vs. Temp

*Note: rolloff at -40C and +85C due to change in SAW filter Fc over temperature

869

872

875

878

881

884

887

890

893

Freq (MHz)

Gain (dB)

-40C

+25C

+85C

Conversion Gain vs. Vdd vs. Temp

2.5

2.6

2.7

2.8

2.9

3.1

3.2

Vdd (volts)

Gain (dB)

-40C

+25C

+85C

IIP3 vs. Vdd vs. Temp

-12

-11

-10

-9

-8

-7

2.5

2.6

2.7

2.8

2.9

3.1

3.2

Vdd (volts)

IIP3 (dBm)

-40C

+25C

+85C

Noise Figure vs. Freq vs. Temp

869

872

875

878

881

884

887

890

893

Freq (MHz)

Noise Figure (dB)

-40C
+25C
+85C

Idd vs. Freq vs. Temp

869

875

881

887

893

Freq (MHz)

Idd (mA)

-40 C

+25 C

+85 C

Idd vs. Freq vs. Vdd

869

872

875

878

881

884

887

890

893

Freq (MHz)

Idd (mA)

Vdd= 2.8v
Vdd= 2.7v
Vdd= 3.0v

TQ9222

Data Sheet

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Typical Performance:

Test Conditions: TQ9222 High Band (Unless Otherwise Specified): Vdd=2.8V, Ta=25C, filter IL=2.5dB, RF=1960MHz, LO=2070MHz, IF=110MHz, LO input=-7dBm

Conversion Gain vs. Freq. vs. Temp.

1930

1940

1950

1960

1970

1980

1990

Freq (MHz)

CG (dB)

-40 C

+25 C

+85 C

Conversion Gain vs. Vdd vs. TEMP

2.5

2.6

2.7

2.8

2.9

3.1

3.2

Vdd (v)

CG (dB)

-40 C

+25 C

+85 C

IIP3 vs. Vdd vs. TEMP

-13

-12

-11

-10

-9

-8

-7

2.5

2.6

2.7

2.8

2.9

3.1

3.2

Vdd (v)

IIP3 (dBm)

-40 C

+25 C

+85 C

Noise Figure vs. Freq. vs. Temp.

1930

1940

1950

1960

1970

1980

1990

Freq (MHz)

NF (dB)

-40 C

+85 C

+25 C

Idd vs Freq. vs Temp.

1930

1940

1950

1960

1970

1980

1990

Freq (MHz)

Idd (mA)

-40 C
+25 C
+85 C

Idd vs Freq. vs Vdd

1930

1940

1950

1960

1970

1980

1990

Freq (MHz)

Idd (mA)

Vdd= 2.7v
Vdd= 2.8v
Vdd= 3.0v

TQ9222
Data Sheet

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Application/Test circuit

Bill of Material for TQ9222 Receiver Application/Test Circuit

Component

Reference Designator

Part Number

Value

Size

Manufacturer

Receiver IC

TQ9222

QSOP-24

TriQuint Semiconductor

Capacitor

1.2pF

0603

Capacitor

C2, C3, C4, C5

1000pF

0603

Capacitor

1.5pF

0603

Capacitor

C7, C10

.01

0603

Capacitor

4.7pF

0603

Capacitor

C8, C11

12pF, 10pF

0603

Capacitor

C12

8.2pF

0603

Capacitor

C13

1.5pF

0603

Capacitor

C14, C15 (filter

dependent)

0.5pF

0603

LO in A

V LNA A

LNA in A

V MX A

IF out B

V IF B

V IF A

LNA in B

LO in B

V LNA B

V MX B

C10

C11

TQ9222

C12

IF out A

TQ9222
Data Sheet

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Introduction

The TQ9222 3V RFIC Downconverter is designed specifically
for dual-band TDMA applications. The TQ9222 contains two
separate LNA+Mixer circuits to handle both the 800 MHz
cellular band and the 1900 MHz PCS band. The IF frequency
range covers 70 to 140 MHz. Most of the ports are internally
matched to 50

simplifying the design and keeping the number

of external components to a minimum. Separate supply voltage
connections provide the required flexibility for dual-band
operation.

Operation:

Please refer to the applications test circuit above.

General Description

Low Noise Amplifier (LNA)

The LNA sections of the TQ9222 consist of two cascaded
common source FETs (see Fig 1). Each LNA is designed to
operate on supply voltages from 3V to 5V. The main differences
between the high and low band LNAs are the bias circuits. The
source terminal of the first stage has to be grounded very close
to the pin (pin 1 for PCS band and pin 12 for cellular band). This
will avoid a significant gain reduction due to degeneration. The
LNA requires a matching circuit on the input to provide a good
noise, gain and return loss performance. The output is close to
50

for direct connection to a 50

image stripping filter.

Fig 1. LNA Sections

Cellular Band Mixer

The cellular band mixer of the TQ9222 is implemented by a
common source depletion FET. The mixer is designed to
operate on supply voltages from 3V to 5V. An on-chip buffer
amplifier simplifies direct connection of the LO input to a
commercial VCO at drive levels down to -7dBm. The common-

gate LO buffer provides a good input match, and supplies the
voltage gain necessary to drive the mixer FET gate. The "open-
drain " IF output allows for flexibility in matching to various IF
frequencies and filter impedances (see Fig. 2).

Fig 2. Cellular Band Mixer

PCS Band Mixer

The PCS band mixer section of the TQ9222 is a balanced
mixer with a single ended output. This balanced mixer topology
minimizes the LO leakage out of the RF and IF ports thereby
giving excellent LO suppression (see Fig. 3)

Fig 3. PCS Band Mixer

Low Noise Amplifier Application

To obtain the best possible combination of performance and
flexibility, the high and low band LNAs were designed to be
used with off-chip input impedance matching. Based on the
system requirements, the designer can make several
performance trade-offs and select the best impedance match for
the particular application.

LNA

out

LNA

Fig 1. TQ9222

Simplified

Schematic of
LNA Section

Vdd

BIAS

LOAD

Mixer IF

Output

Mixer RF

Input

Mixer LO

Input

LO Bias and

Tuning

Mixer IF

Output

Mixer RF

Input

Mixer LO

Input

Vdd

TQ9222

Data Sheet

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LNA Input Match

The input matching network primarily determines the noise and
gain performance. Fig 4 shows a suggested input match for the
high band. The low band uses a series 1.2pF capacitor and a
shunt 10nH inductor.

Fig 4. LNA Input Match

The LNA gain, noise figure and input return loss are a function
of the source impedance (Z

), or reflection coefficient (

presented to the input pin. Highest gain and lowest return loss
occur when

is equal to the complex conjugate of the LNA

input impedance. A different source reflection coefficient,

opt

which is experimentally determined, will provide the lowest
possible noise figure, F

min

The noise resistance, R

, provides an indication of the sensitivity

of the noise performance to changes in

as seen by the LNA

input.

(

)

LNA

MIN

opt

Components such as filters and mixers placed after the LNA
degrade the overall system noise figure according to the
following equation:

SYSTEM

LNA

where F

LNA

and G

LNA

represent the linear noise factor and gain

of the LNA and F

is the noise factor of the next stage. Thus, the

system noise figure depends on the highest gain and minimum
noise figure of the LNA.

Designing the input matching network involves a compromise
between optimum noise performance and best input return loss.
For example, when the TQ9222 LNA is matched for optimum
noise figure (1.35dB @ 880 MHz, and 1.45dB @ 1960 MHz),
the input return loss is only about 4dB. On the other hand,
when the LNA is matched for best return loss, the LNA noise
figure is approximately 1.95dB @ 881 MHz and 2.14dB @
1960MHz (see Table 1.)

Table 1. Noise Parameters

LNA Output Match

The output impedance of the high and low band LNAs, were
designed to interface directly with 50

terminations. This

internal match serves to reduce the number of external
components required at this port. An additional benefit accrues
as an improvement in IP3 performance, return loss and power
gain.

Low Band LNA Output

The output of the low band LNA will most often be connected to
an image stripping filter. Depending on the filter type, additional
components might be needed to present a better match to the
LNA output. The TQ9222 general applications circuit shows a
TOYOCOM (637-881A) saw filter for the low band. A series
inductor "L8" of 10nH is added to the filter input to improve the
match. This series inductor also smoothes out excessive ripple
in the filter passband improving the overall performance of the
circuit.

Note: These values assume ideal components and neglect board parasitics.

The discrepancy between these values and those of the typical application

circuit are the board and component parasitics.

10nH

1.2pF

Pin 2

Low Band

835

0.678

1.34

61.6

850

0.655

1.38

61.1

865

0.652

1.36

61.2

880

0.652

1.35

60.9

895

0.649

1.36

61.3

910

0.659

1.35

61.2

925

0.687

65.6

1.35

Freq

opt|

opt

Fmin

(MHz)

(dB)

()

High Band

1860

0.557

1.44

31.1

1960

0.555

1.45

31.7

2060

0.532

1.61

29.0

Freq

opt|

opt

Fmin

(MHz)

(dB)

()

TQ9222
Data Sheet

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High Band LNA Output

The output of the high band LNA can also be connected directly
to the image stripping filter. However, it has been found that
some SAW filters can cause low image rejection in the circuit as
a whole, even as their individual characteristics show rejection
of 30-40dB. It appears that the very low impedance of the SAW
filter at the image frequency can be reflected back to the LNA
output pin, lessening the effectiveness of the ground, and
leaking into the mixer input.

The optimum solution would be to include a 1/4 wavelength
transmission line between the LNA output and SAW input in
order to invert the impedance. However, a more compact
solution is to bridge a small capacitor across a much shorter
transmission line, giving a much longer effective length. (refer to
Fig 9). It may also be possible to entirely use lumped
components to accomplish the same. On the evaluation board,
the transmission line is looped to that the capacitor can be
varied in its positioning, thus facilitating tuning.

Low Band Mixer: LO Port

As mentioned earlier, a common gate buffer amplifier is
positioned between the LO port and the mixer FET gate in order
to provide a good impedance to the VCO and to allow operation
at lower LO drive levels. The buffer amplifier provides the
voltage gain needed to drive the gate of the mixer FET while
consuming very little current (approximately 1.5mA).

Because of the broadband 50

input impedance of the buffer

amplifier and the internal DC blocking capacitor, the user's VCO
can be directly connected to the LO input via a 50

line with no

additional components.

Low Band Mixer Input

Although the low band mixer input port has been designed with
a 50

impedance, it has been found that LO leakage out

through the pin can in some cases reflect off the SAW filter and
travel back to the mixer input out of phase, causing some
degradation in conversion gain and system noise figure.
Sensitivity to the phenomena depends on the particular filter
model and SAW-mixer transmission line length. On the

evaluation board, a small inductance "L8" is added on the SAW
output to compensate. With certain longer line lengths it is
possible to omit "L8".

Low Band LO Buffer Tune

While the broadband input match of the LO buffer amplifier
makes interfacing easy, the broadband gain means that thermal
and induced noise at other frequencies can be amplified and
injected directly into the LO port of the mixer. Noise at the IF
frequency, and at LO +/- IF will be downconverted and emerge
at the IF port, degrading the downconverter noise figure.

As indicated on the diagram of Fig 5, in order to test the LO
response to these spurious signals, a two-tone signal was
injected into the LO port with the RF port terminated in 50

One signal generator is set to the LO frequency at its normal LO
drive level usually (-7 dBm). The second signal generator
(spurious signal) is set to the LO +/- the IF frequency. The
combined input power at mixer LO port has to be less than -50
dBm. The results shown in Table 2 indicate a good suppression
of the interfering signals.

Fig. 5 LO Spurious Response Diagram

LO/Spurious

(MHz)

Mixer LO Port

Input Power

C/V

(dB)

991/1101

-57

-71.7

991/1101

-58.9

-71.8

Table 2. LO Spurious Response Data

TQ9222 Mixer

Directional

Coupler

50 ohm

SIG 1:

FLO

SIG 2:

FLO +/- IF

Spectrum

Analyzer

TQ9222

Data Sheet

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Calculation of Nominal L Value

The node between the LO buffer amplifier and the mixer FET is
brought out to Pin 7 (L_tune) and connected to a shunt inductor
to AC ground. This inductor is selected to resonate with internal
capacitance at the L0 frequency in order to suppress out-of-
band gain and improve noise performance.

The internal capacitance of the LO amplifier output plus the
stray capacitance on the board surrounding Pin 7 is
approximately 1.8 pF. The inductor is selected to resonate with
the total capacitance at the LO frequency using the following
equation:

(

)

where C

1 5

but must be confirmed with measurements on a board
approximating the final layout.

Measuring the LO Frequency Response

The frequency response of the LO driver amplifier can be
measured using a semi-rigid probe (see Fig. 6) and a network
analyzer.

Connect port 1 to the LO input (Pin 8) of the TQ9222 with the
source power set to deliver -7 dBm. Connect the coaxial probe
to Port 2 and place the probe tip approximately 0.1 inch away
from either Pin 7 or the inductor.

Fig 6. LO Buffer Amplifier Tuning

If the calculated shunt inductor (L2) is not a standard value, the
AC ground, implemented with C3, can be slide along the
transmission line to adjust for the right inductance (see Fig 7).
Once this is completed, the peak of the response should be
centered at the center of the LO frequency band.

Fig 7. Adjusting AC Ground

Mixer IF Port

The Mixer IF output is an "open-drain" configuration, allowing for
flexibility in efficient matching to various filter types and at
various IF frequencies.

For evaluation of the LNA and mixer, it is usually necessary to
impedance match the IF port to the 50

test systems. When

verifying or adjusting the matching circuit on the prototype circuit
board, the LO drive should be injected at pin 8 for the Low Band
and pin 5 for the High Band at the nominal power level of -7
dBm, since the LO level does have an impact on the IF port
impedance.

There are several networks that can be used to properly match
the IF port to the SAW or crystal IF filter. The mixer supply
voltage is applied through the IF port, so the matching circuit
topology must contain either an RF choke or shunt inductor. An
extra DC blocking capacitor is not necessary if the output will be
attached directly to a SAW or crystal bandpass filters.

Figure 8 shows the IF matching network for the low band. A
shunt L, series C, shunt C, is the simplest and requires the
fewest components. The only difference with the high band is
the series capacitor value of 10pF as opposed to 8.2pF. DC
current can be easily injected through the shunt inductor and the
series C provides a DC block, if needed. The shunt C, is used
to reduce the LO leakage.

Probe

TQ9222

Network

Analyzer

Port 1 Port 2

-30
-32
-34
-36
-38
-40
-42

S21 (dB)

1000

Frequency (MHz)

1100 1200

900

800

700

Ground

TQ9222

Placement of inductor

will adjust between

standard values

TQ9222
Data Sheet

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Fig. 8 Suggested IF Match

Half-IF Application

When the intermediate frequency is less than twice the
bandwidth of the receiver, Half-IF intermodulation spurs will fall
within the frequency of operation. The image filter and mixer are
the main circuit blocks that influence Half-IF spur suppression.
However, it was shown experimentally that the preselector filter
plays an important role as well in suppressing half-IF and image
spurious signals. The preselector filter eliminates out of band
spurs that could get amplified and degrade the performance.

A narrow band pass filter and a high IF frequency are best to
eliminate Half-IF problems. The other major contribution is mixer
balance which is affected by two factors. First, the LO signal that
leaks into the mixer inputs via parasitics. The second major
contribution is the source impedance presented at the mixer RF
input port. Depending on the board layout, the optimum mixer
source impedance may shift which will degrade the Half-IF
performance.

It is possible to optimize mixer source impedance for Half-IF
rejection at the LO frequency only. This will avoid affecting the
desired signal to a large degree. Experience with the TQ9222,
has shown that optimum mixer source impedance results in a
significant mismatch causing gain reduction. Therefore, a trade-
off has to be made between optimum Half-IF performance and
conversion gain.

The standard TQ9222 evaluation board uses a Toko TDFM1B-
1960L-11 dielectric filter in the high band. It was found that an L-
network, comprised of a series 1.8 nH inductor and a shunt 1.8
pF capacitor on the mixer input, produces the best Half-IF
rejection and conversion gain. To a lesser extent, it was found

that the length of the transmission line in the filter input also has
an effect on Half-IF performance.

Fig. 9 Image and Half-IF circuit

Note that if the final board layout is significantly different from
our evaluation board, the network shown will only be useful as a
guideline for development or to show what performance is
possible with the TQ9222. A SAW filter will probably require a
totally different type of network; and network component values
vary widely between SAW filter models.

Usually only a portion of the frequency band will be of concern
for half-IF interference. It will depend on the injection mode of
the LO signal and the IF frequency being used. For example If
the LO is a high side injection such as the case of the TQ9222
and the IF = 110 MHz then (theoretically) we worry about the
first 5 MHz of the band (1930-1935) only if we have ideal filters.
Unfortunately most of the image stripping filters roll-off around
2000 MHz or higher hence the need to optimize performance up
to 1945 MHz. The opposite occurs for low side LO.

Since the frequency response of the preselector and image
stripping filter help the performance at the high end of the band,
the TQ9222 was tuned to give good half-IF rejection at the low
end of the band over a wide temperature range (-40

C to +85

C). That was accomplished with a Pi-network* (between the

filter output and the mixer input) comprise of a series L = 2.2
nH, shunt C = 1.0 and 0.5 pF. As expected this tuning network
degraded the half-IF performance from 1970 to 1990 MHz
specially at the extremes temperatures. However, once the

Note: These values assume ideal components and neglect board parasitics.
The discrepancy between these values and those of the typical application
circuit are the board and component parasitics

Vdd

Mx IF

out

0.01uF

Pin 14

180nH

10pF

8.2pF

TQ9222

1.8pF

1.8nH

700 mils from pin

to filter input

TQ9222

Data Sheet

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downconverter was tested with the preselector filter, the
performance improved significantly. The results are shown in
Table 3.

Freq Temp

Half-IF

(MHz) (

C) (dB)

1930

-40

70.30

1940

-40

71.72

1980

+85

72.46

1990

+85

70.21

Table 3. TQ9222 Performance with Preselector Filter (IF = 110
MHz, PLO = -7 dBm, Vdd = 2.8v)

The preselector filter not only improved the half-IF performance
but also the image rejection up to 70 dB, RF to IF isolation up to
33dB, and LO to IF isolation up to 43dB.

*This is one of many different circuit topologies that could give similar results.
The circuit selected that gives the best performance will depend on the PCB
layout.

TQ9222
Data Sheet

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www.triquint.com

Package Pinout

Pin Descriptions

Pin Name

Pin #

Description and Usage

LNA GND 1900

High-band LNA first-stage ground connection. Direct connection to ground.

LNA IN 1900

High-band LNA input. DC blocked, requires external matching elements for noise match and match to 50

Vdd LNA 1900

High-band LNA supply voltage. Local bypass cap required.

MXR LO 1900

High-band Mixer LO input. Internally DC blocked. L3 required for 50

match.

Vdd MXR 1900

High-band Mixer LO buffer supply voltage. Local bypass cap required.

Vdd MXR 800

Low-band Mixer LO buffer supply voltage. Local bypass cap required.

MXR LO 800

Low-band Mixer LO input. Matched to 50

. Internally DC blocked.

Vdd LNA 800

Low-band LNA supply voltage. Local bypass cap required.

LNA IN 800

Low-band LNA input. DC blocked, requires external matching elements for noise match and match to 50

GND LNA 800

Low-band LNA first-stage ground connection. Connection to ground.

N/C

Open pin. No connection.

LNA OUT 800

Low-band LNA output. Matched to 50

. Internally DC blocked.

Vdd MXR 1900

Vdd MXR 800

MXR LO 800

MXR LO 1900

LNA GND 1900

GND

LNA IN 1900

Vdd LNA 1900

TQ9222

Vdd LNA 800

GND

LNA IN 800

LNA GND 800

N/C

LNA OUT 1900

GND

MXR RF 1900

IF TUNE

MXR IF 1900

MXR IF 800

GND

MXR RF 800

GND

LNA OUT 800

N/C

TQ9222

Data Sheet

For additional information and latest specifications, see our website:

www.triquint.com

MXR RF 800

Low-band Mixer RF input. Matched to 50

, internally DC blocked.

MXR IF 800

Low-band Mixer IF output. Open-drain output. Connection to Vdd required, external matching is required.

MXR IF 1900

High-band Mixer IF output. Open-drain ouput. Connection to Vdd required, external matching is required.

IF TUNE

Half-IF tuning inductor to ground for optimum half-IF performance in the high-band mixer.

MXR RF 1900

High-band Mixer RF input. Matched to 50

, internally DC blocked.

LNA OUT 1900

High-band LNA output. Matched to 50

, internally DC blocked.

N/C

Open pin. No connection.

GND

3, 10, 15,

17, 22

Ground connection. Use several via holes immediately adjacent to the pins down to backside ground plane.

TQ9222

Data Sheet

Additional Information

For latest specifications, additional product information, worldwide sales and distribution locations, and information about TriQuint:

Web: www.triquint.com

Tel: (503) 615-9000

Email: info_wireless@tqs.com

Fax: (503) 615-8900

For technical questions and additional information on specific applications:

Email: info_wireless@tqs.com

The information provided herein is believed to be reliable; TriQuint assumes no liability for inaccuracies or omissions. TriQuint assumes no responsibility for the use of
this information, and all such information shall be entirely at the user's own risk. Prices and specifications are subject to change without notice. No patent rights or
licenses to any of the circuits described herein are implied or granted to any third party.
TriQuint does not authorize or warrant any TriQuint product for use in life-support devices and/or systems.
Copyright © 1998 TriQuint Semiconductor, Inc. All rights reserved.
Revision B, December 1, 1998

For additional information and latest specifications, see our website:

www.triquint.com

Ð­Ð»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: TQ9222

ÐÐ»ÐµÐºÑ‚Ñ€Ð¾Ð½Ð½Ñ‹Ð¹ ÐºÐ¾Ð¼Ð¿Ð¾Ð½ÐµÐ½Ñ‚: TQ9222